Transmission network for emphasizing the high-frequencies of applied oscillations



April 8, 1952 G. HEPP 2,591,936

TRANSMISSION NETWORK FOR EMPHASIZING THE HIGH-FREQUENCIES OF APPLIED OSCILLATIONS Filed Feb. 12, 1947 i 4 O 17%;, 47' c. HEPP INVENTOR AGENT Patented Apr. 8, 1952 TRANSMISSION NETWORK FOR EMPHASIZ- ING THE HIGH-FREQUENCIES OF APPLIE OSCILLATIONS Gerard Hepp, Eindhoven, Netherlands, assignor to Hartford National Bank and Trust Company, Hartford, Conn., as trustee Application February 12, 1947, Serial No. 728,046 7 In the Netherlands July 6, 1944 Section 1, Public Law 690, August 8, 1946 Patent expires July 6, 1964 Claims.

This invention relates to a network for the transmission of electric oscillations, in which the high frequencies are favoured above the low frequencies. Such a network is used for example in transmitters for the transmission of frequencymodulated oscillations, this emphasizing of the high frequencies being referred to as pre-emphasis. This pre-emphasis has the advantage of greater anti-interference, the high modulation frequencies, which generally have a low amplitude, being favoured to such an extent as to be caused to lie above the interference level. The said favouring of the high modulation frequencies must naturally be undone in the receiver prior to reception. It is therefore necessary for favouring the high frequencies to fix a norm to be taken into account when designing the receiver. As normal pre-emphasis is generally looked upon the relative favouring of the high modulation frequencies, as is secured by feeding the modulating oscillations to an amplifying valve whose anode circuit includes the series combination of an inductance coil and a resistance, the ratio between inductance and resistance yielding a time constant of about 10- sec. In this case, the amplification of the high modulation frequencies is about tenfold that of the low frequencies.

A disadvantage of these circuit arrangements is that the inductance has to be so low that the tube capacities are still of no importance and this, in view of the prescribed time constant value of 10- sec., due to the ratio between inductance and resistance, leads to very low values for the resistance. Thus, if the said amplifying valve is coupled to the final stage of the amplifier and the latter has a strong negative feedback in order to reduce the non-linear distortion (the permissible distortion in such an amplifier lies far below 1%), the amplitude of the modulating oscillation fed to the grid of the amplifier valve must be large, so that, at a low value of the resistance in the anode circuit, the tube has passing through it a high anode-current and this entails considerable distortion. It is frequently impossible to suppress this distortion by negative feedback of the amplifier, because the total amplification no longer sufiices in this case, since it is found to be practically impossible to ensure sufficient amplification throughout a large frequency zone at the desired'low distortion.

A further method of securing pre-emphasis consists in that the negative feedback circuit of the amplifier for the modulating oscillations includes a network which is constituted in such manner that the low frequencies are negatively back-coupled to a greater extent than the high frequencies. In order to secure a normal preemphasis the negative feedback of the low frequencies must be about tenfold that for the high frequencies and at such a strong negative feedback for the low frequencies the amplifier tends to self-oscillate.

The invention has for its object to provide a network for pre-emphasis that can be included in the input circuit of an amplifier, with the result that the disadvantages inherent in the well-known circuit arrangements are avoided.

According to the invention, the network includes the series combination of two impedances inserted between the input terminals, one of the impedances being constituted by the parallel combination of a resistance R and a condenser C and the other by the parallel combination of a resistance R and an inductance L, -said circuit elements being so proportioned that and the last-mentioned impedance being inserted between the output terminals of the network via a step-up transformer in series with the firstmentioned impedance.

In order that the invention may be clearly understood and readily carried into effect, it will now be described more fully with reference to the accompanying drawing, in which three embodiments of the network according to the invention are illustrated. In the network shown in Fig. 1, the input terminals have inserted between them the series combination of two impedances 3 and 4. The former is constituted by the parallel combination of a resistance R and a condenser C and the latter by the parallel combination of a resistance R. and an inductance L, which is formed by the primary inductance of a step-up transformer 5 whose ratio of transformation is lmz.

If theoutput terminals 6. I are practically unloaded and the input terminals I, 2 have sup plied to them a voltage E1, the output voltage E2 is:

R jwL 2 1+jwC'R A E 1+WRE ii 1 l-kjwClR ir or if is assumed to be --R. and

is assumed to be =CR=p 7 zl E2-- +1., 6 E

If nzfl is equalized with 10- sec., a normal preemphasis, apart from the factor 1+;iwfl in'the nominator, is obtained. This factor -1-'|-1'w 3'is negligible in many cases, that is to say if the ratio of. transformation m islhigh. 1 If forexample lthel highest "frequencytoxbetransmitted' is to be favoured over the. lowest'frequencies .by. afactor ..l0,asoithat @7126. is 10 at. this frequency,

-so'that for:n2 10,-.is up in the nominator-is negligible: relatively to 1. If this-is not permissible,- a correction must be made. The required correc- -tion is however "so small thatit can -.-be made simply by means of a network in-the amplifier itself or in the negative feedback circuit.

.Thernetwork shownin Fig; 2.-is distinguished from that in Fig. 1 in thatialsotthe impedance 3 I is included'between the-outputterminals via a transformer.- 8 v whose: ratio 1 of: transformation 1 n1. Assuming the primary. inductance of this transformer to be solarge that \the impedance formed thereby is. negligible relatively to the im- =pedance 3,:the'output voltage Eais given by:

mustbe-equal to 10- sec. The ratio: of. transformation a n1 shou'ld be' 10w as compared with the ratio of transformation ."nz.

Alternatively, as shown in-" F'ig; 3,:instead-of ".connecting-Ithe resistance Rshown in-Fig; 1 in parallel with the-primary of the transformer 5, a resistance nz R' may be connected -in parallel with the secondary. Z This maybe'advantageous "under certain cndi-tio'ns,'f0r eXampleif the out- '-put'terminals- 6 1- of the network are loaded by a I resistance. In that"case,-the load rresistance:

may-be connected to'the network in such manner lthat a resistance R is connectediinsparallelwith 'thecondenser (land a"resistancema i-R:in parallel with the secondary of the transformerigthe network-behaving: in quite the 1 same: manner as the network shown Figure 1.

The network according to! the: invention, -as stated hereinbefore, may be included :in the input circuit of anamplifier. JInIthiS. case; the'rtrans- "former- 8 showmin-Eig. zrmay-be constituteduby the input transformer already included in the input circuit of the amplifier.

In this case, as shown in Fig. 4, it is preferable that with a push-pull input circuit of the amplifier the primary of the transformer 5 and the resistance R should be split up into two equal halves which should be arranged on either side $01 the primaryU-of the transformer 8Iso' that the symmetry of the input circuit'with respect to earth is conserved.

What I claim is: J 1.: A:four'.termina1 network adapted to empha- :Jsize' the high: frequencies relative to the low frequencies' of oscillations transmitted therethrough,

.15 said network comprising input and output termi- .Iials, avoltage' step-up transformer having a primary windingand a secondary winding, 2. first impedance constituted by the primary winding "connectedin parallel relation with a first resistzoance; and a second impedance constituted by a capacitance connected in parallel relation with a second resistance having the same value as said first resistance, said first and second impedances being-serially connected across the input terminals, said secondary winding being connected in ="serieswith :said secondiimpedanceacross the out- "put terminals.

2. A- four terminal network adapted to emphasize the high frequencieslrelative I tov the low'frequencies of oscillations transmitteditherethrough,

s said'-"net\vork-- comprising: input and output ter- --min'a1s, a voltagestep-uptransformer having, a primary windingand a secondarywinding, afirst '-impe'dance constituted by said primary winding *1 connected in parallel relation with a resistor, and

a second impedance constituted by a capacitor connected in 'pa-i 'allel relation with a resistonsaid first "and-second imp'edances being serially con- "nested across the'input terminals,v said secondary 40 winding beingconnected in series with said sec- '-ond' impedance acrossthe output terminals, the elements comprising said network having values at which the following relationship exists:

Where-L is the' inductance of: said primary Winding (3 is" the' capacit'ance'of said capacitor and 'R- is the resistance of'theresistor in saidl'first 7 1: "impedance-and the resistorin saidlsecond im- In order to obtain the normal pre-emphasis,

' ped'ance.

3. A-"fourterminal network adapted: to 'emphasize the high frequencies relative to the low frequencies of audio-frequency oscillations.v trans- 'initted therethrough, said network comprising =input ahd output terminals, afirst voltage stepi up-transformer having, alprimary winding and a second winding, a first impedance constituted by the primarycivinding connected in parallel relago tiol'i with airesistor', azsecond impedance network :cons'tituted by aicapacitorcconnected in parallel irelation with a resiston'the resistors of said impedancesi'having thesame'value, saidfirst and second impedances being:serially connected across g l-said input: terminals, and a-secondrvoltage stepmpi'transfovmer having a primary winding: connected -across saidisecond impedance and asec- :tondary windingconnected in series with the sec- !Jondary win'ding of saidvfirst transformeracross --sa;id output:'terminals said first transformer havhing aLgreater :step-up: ratioi: than said second transformer.

4;:.A.four :terminal network adapted-to emphasize therhighifrequencies relative .to the. lowfrequencies r ;jof.-- "audio +frequency oscillations transmitted therethrough, said network comprising input and output terminals, a first voltage step-up transformer having a primary winding and a second winding, a first impedance constituted by the primary winding connected in parallel relation with a resistor, a second impedance network constituted by a capacitor connected in parallel relation with a resistor, said first and second impedances being serially connected across said input terminals, and a second voltage step-up transformer having a primary winding connected across said second impedance and a secondary winding connected in series with the secondary winding of said first transformer across said output terminals, the elements comprising said network having values at which the following relationship exists:

where L is the inductance of the primary winding of the first transformer, C is the capacitance of said capacitor and R is the resistance of the resistor in said first impedance and the resistor in said second impedance.

5. A four terminal network adapted to emphasize the high-frequencies relative to the lowfrequencies of audio oscillations transmitted therethrough, said network comprising input and output terminals, a voltage step-up transformer having a primary winding and a secondary winding, a first impedance constituted by the primary winding connected in parallel relation with a first REFERENCES CITED The following references are of record in the file of this patent:

UNITED STATES PATENTS Number Name Date 1,959,494 Nyquist May 22, 1934 1,976,504 Lucas Oct. 9, 1934 2,025,128 Rust Dec. 24, 1935 zpeawe Roberts June 9, 1936 2,159,944 Roberts May 23, 1939 2,176,200 Blumlein Oct. 1'7, 1939 2,282,113 Brailsford May 5, 1942 OTHER REFERENCES Proceedings of the Radio Club of America, v01. 7, No. 9, September 1930. Pp 91-96 (6 pages) Design and Application of Adjustable Tone Compensating Circuits. J. G. Aceves. 1'78-44.13A. Copy available in the Library of Congress, Washington, D. C. 

